Semiconductor Device and Method of Driving the Same

ABSTRACT

To provide a semiconductor device and a driving method of the same that is capable of enlarging a signal amplitude value as well as increasing a range in which a linear input/output relationship operates while preventing a signal writing-in time from becoming long. The semiconductor device having an amplifying transistor and a biasing transistor and the driving method thereof, wherein an electric discharging transistor is provided and pre-discharge is performed.

This application is a continuation of copending application Ser. No.14/697,232 filed on Apr. 27, 2015 which is a continuation ofapplication. Ser. No. 14/247,764 filed on Apr. 8, 2014 (now U.S. Pat.No. 9,019,408 filed on Apr. 28, 2015) which is a continuation ofapplication Ser. No. 13/737,112 filed on Jan. 9, 2013 (now U.S. Pat. No.8,743,250 issued Jun. 3, 2014) which is a continuation of applicationSer. No. 13/525,653 filed on Jun. 18, 2012 (now U.S. Pat. No. 8,355,065issued Jan. 15, 2013) which is a continuation of application Ser. No.12/895,022 filed on Sep. 30, 2010 (now U.S. Pat. No. 8,203,636 issuedJun. 19, 2012) which is a continuation of application Ser. No.11/650,671 filed on Jan. 8, 2007 (now U.S. Pat. No. 7,808,535 issuedOct. 5, 2010) which is a divisional of U.S. application Ser. No.09/829,114, filed on Apr. 9, 2001 (now abandoned), all of which areincorporated herein by reference.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a semiconductor device and a drivingmethod thereof. Specifically, the present invention relates to an MOSsensor device that has an image sensor function and to a driving methodof the same.

2. Description of the Related Art

In recent years, the use of information equipment such as a personalcomputer has spread widely, and hence the demand to read (store) variousinformation in the personal computer, etc. as electronic information isrising. Therefore, replacing the conventional silver salt camera, adigital still camera or a scanner, which is used as a means of readinginformation printed on paper, are in the spotlight.

An area sensor in which the pixels are arranged in a two-dimensional wayis used in the digital still camera. In the scanner, a copier machine,etc., a line sensor in which the pixels are arranged in aone-dimensional way is used. In the case of using the line sensor toread a two-dimensional image, signals are read while moving the linesensor.

A CCD type sensor is mainly used as the image sensor in these types ofimage reading equipments. In the CCD type sensor, a photoelectricconversion is carried out in a photo diode of each of the pixels andthen the CCD is used to read those signals. However, an MOS type sensorthat is formed by using a single crystal silicon substrate is showingsigns of popularization in apart of the technical field thereof by usingfactors such as the incorporation of a peripheral circuit, manufacturingit into one chip, its suitability for a real time signal process, andits low consumption power as weapons. Further, the manufacture of an MOStype sensor by using a TFT that is formed on a glass substrate is beingdeveloped at the research level. In the MOS type sensor, thephotoelectric conversion is carried out in the photo diode of each ofthe pixels, whereby the signals of the respective pixels are read out byusing a switch that is formed by an MOS transistor.

As a pixel structure of the MOS type sensor, various types are beingdeveloped. The various types of pixel structure of the MOS type sensorcan be largely categorized into two types, that is, a passive sensortype and an active sensor type. The passive sensor is a sensor in whicha signal amplitude element is not incorporated into the respectivepixels whereas the active sensor is a sensor in which a signal amplitudeelement is incorporated into the respective pixels. The active sensorhas an advantage over the passive sensor in that it is strong againstnoise because the signals are amplified in each of the pixels.

Shown in FIG. 2 is an example of a circuit of a pixel in the passivesensor. A pixel 10005 is composed of a switching transistor 10001 and aphoto diode 10004. The photo diode is connected to a power sourcestandard line 10006 and to a source terminal of the switching transistor10001. Agate signal line 10002 is connected to a gate terminal of theswitching transistor 10001, and a signal output line 10003 is connectedto a drain terminal thereof. Photoelectric conversion takes place in thephoto diode 10004. In other words, an electric charge is generated inresponse to the incidence of light, whereby the electric charges areaccumulated therein. Then the switching transistor 10001 is made intoconductive by controlling the gate signal line 10003 to thereby read outthe electric charge of the photo diode 10004 through the signal outputline 10003.

There are various kinds of pixel structure of the active sensor. Pixelstructures such as a photo diode type and a photo gate type and theiroperations are introduced in IEDM95: p. 17: CMOS Image Sensors, ElectricCamera On a Chip or in IEDM97: p. 201: CMOS Image Sensors—RecentAdvances and Device Scaling Considerations. In the ISSCC97: p. 180: A ¼Inch 330 k Square Pixel Progressive Scan CMOS Active Pixel Image Sensor,the pixel structure is categorized from the perspective of a selectingmethod of the pixel. That is, a case of whether to use a transistor or acapacitance as a selecting element is described therein. Thus, there arevarious types of structures regarding the number of transistors forforming one pixel. A general description of the CMOS type sensor isbroadly introduced in the JIEC Seminar: Development Prospects of theCMOS Camera: Feb. 20, 1998. In the description thereof, a logarithmconversion form, which outputs a signal of the logarithm of lightdensity by connecting a gate electrode and a drain electrode of aresetting transistor, is also explained.

As shown in FIG. 3, a pixel structure of the active sensor that ismostly adopted is a type that is composed of three N channel transistorsand one photo diode, thereby forming one pixel 308. A P channel sideterminal of a photo diode 304 is connected to a power source standardline 312, and an N channel side terminal of the photo diode 304 isconnected to a gate terminal of an amplifying transistor 306. A drainterminal and a source terminal of the amplifying transistor 306 areconnected to a power source line 309 and to a drain terminal of aswitching transistor 301, respectively. A gate terminal of the switchingtransistor 301 is connected to a gate signal line 302 while a sourceterminal thereof is connected to a signal output line 303. A gateterminal of a resetting transistor 307 is connected to a reset signalline 306. A source terminal and a drain terminal of the resettingtransistor 307 are connected to the power source line 309 and a gateterminal of the amplifying transistor 306, respectively.

In the case of an area sensor, not only one pixel 308 is connected toone signal output line 303, but also a plurality of pixels are connectedthereto. However, one biasing transistor 311 is connected per signaloutput line 303. Agate terminal of the biasing transistor 311 isconnected to a bias signal line 310. A source terminal and a drainterminal of the biasing transistor 311 are connected to the signaloutput line 303 and to a biasing power source line 313.

Next, a basic operation of the pixel 308 will be explained.

The resetting transistor 307 is first made into a conductive state.Because the P channel side terminal of the photo diode 304 is connectedto the power source standard line 312, whereby the photo diode 304becomes a state in which the N channel side terminal is electricallyconnected to the power source line 309, an inverted bias voltage isapplied to the photo diode 304. Hereinafter, the operation of chargingthe N channel side terminal of the photo diode 304 until its electricpotential is equivalent to the electric potential of the power sourceline 309 will be referred as “reset”. Thereafter, the resettingtransistor 307 is made into a non-conductive state. When light is beingirradiated to the photo diode 304, an electric charge is generated dueto a photoelectric conversion. Therefore, as time elapses, the electricpotential of the N channel side terminal of the photo diode 304, whichhas been charged up to the electric potential of the power source line309, gradually becomes smaller because of an electric charge that wasgenerated by the light. Then after a fixed period of time has passed,the switching transistor 301 is made into a conductive state, whereby asignal is output to the signal output line 303 through the amplifyingtransistor 306.

However, at the time the signal is being output, an electric potentialis applied to the bias signal line 310 to cause a current to flow in thebiasing transistor 311. Therefore, the amplifying transistor 306 and thebiasing transistor 311 operate as the so-called source followercircuits.

An example of the most basic source follower circuit is shown in FIG. 4.In FIG. 4, the case of using the N channel transistor is described.Although a P channel transistor can be used to construct the sourcefollower circuit, a case of using an N channel transistor is shown inFIG. 4. A power source electric potential Vdd is applied to an amplifierside power source line 403. A standard electric potential 0V is appliedto a bias side power source line 404. A drain terminal of an amplifyingtransistor 401 is connected to the amplifier side power source line 403while a source terminal thereof is connected to a drain terminal of abiasing transistor 402. A source terminal of the biasing transistor 402is connected to the bias side power source line 404. A bias electricpotential Vb is applied to a gate terminal of the biasing transistor402. Therefore, a bias current Ib flows in the biasing transistor 402.The biasing transistor 402 basically operates as a fixed electriccurrent source. A gate terminal of the amplifying transistor 401 servesas an input terminal 406. An input electric potential Vin is thusapplied to the gate terminal of the amplifying transistor 401. A sourceterminal of the amplifying transistor 401 serves as an output terminal407, and therefore an output electric potential Vout is applied to thesource terminal of the amplifying transistor 401. At this point, therelationship of the input/output of the source follower circuit becomesVout=Vin−Vb.

In the case of comparing the circuit configurations of FIG. 3 and FIG.4, the amplifying transistor 306 corresponds to the amplifyingtransistor 401, and the biasing transistor 311 corresponds to thebiasing transistor 402. Because it is assumed that the switchingtransistor 301 is in conductive, it can be observed that a switchingtransistor is omitted in FIG. 4. The electric potential of the N channelside terminal of the photo diode 304 corresponds to the input electricpotential Vin (the gate electric potential of the amplifying transistor401, that is, the electric potential of the input terminal 406). Theelectric potential of the signal output line 303 corresponds to theoutput electric potential Vout (the source electric potential of theamplifying transistor 401, that is, the electric potential of the outputterminal 407).

Therefore, in FIG. 3, if the electric potential of the N channel sideterminal of the photo diode 304 is Vpd, the electric potential of thebias signal line 310, that is, the bias electric potential is Vb, theelectric potential of the signal output line 303 is Vout, and theelectric potential of the power source standard line 312 and the biasside power source line 313 is 0V, then the relationship becomesVout=Vpd−Vb. Accordingly, when the electric potential Vpd of the Nchannel side terminal of the photo diode 304 changes, then Vout alsochanges. As a result, the change of the Vpd can be output as a signaland the light intensity can thus be read.

The basic operation of the source follower circuit is one as describedabove. However, the operating principle of the source follower circuitwill be explained next in detail because it is needed for explaining theoperation of the present invention. For simplification, it is assumedthat the sizes and characteristics of the amplifying transistor and thebiasing transistor are the same in the explanation here. Further, anelectric current characteristic of the transistors is an ideal one, thatis, even if a voltage between the source and the drain changes, it isassumed that an electric current value in a saturated region does notchange.

First, as shown in FIG. 4, the bias electric potential Vb is applied tothe gate terminal of the biasing transistor 402. In the case the biasingtransistor 402 operates in the saturated region, the electric current Ibflows therein as shown in FIG. 5. On the other hand, the same amount ofelectric current will flow in amplifying transistor 401 and the biasingtransistor 402 under a fixed normal state because both transistors areconnected in series. Therefore, when the electric current Ib is flowingin the biasing transistor 402, the electric current Ib is also flowingin the amplifying transistor 401. In order to cause the electric currentIb to flow in the amplifying transistor 401, it is necessary to make thevoltage Vgs between the gate and the source of the amplifying transistor401 equivalent to the bias electric potential Vb.

Thus, the output electric potential Vout in the source follower circuitis obtained. The amount of electric potential of the output electricpotential Vout that is lower than the input electric potential Vin isequal to only that of the voltage Vgs between the gate and the source ofthe amplifying transistor 401. Therefore, the input/output relationshipbecomes Vout=Vin−Vgs. The voltage Vgs between the gate and the source ofthe amplifying transistor 401 is equal to the bias electric potentialVb, and hence the input/output relationship becomes Vout=Vin-Vb.However, as shown in FIG. 5, this equation is only valid when thebiasing transistor 402 operates in the saturated region (corresponds tothe case when Vin is large). In the case Vin is small and the biasingtransistor 402 operates in a linear region, the equation Vout=Vin−Vbcannot become valid as shown in FIG. 6. When the biasing transistoroperates in the linear region, the input/output relationship becomesVout=Vin−Vb′. The Vb′ here is the voltage between the gate and thesource of the amplifying transistor 401 at that point. If the electriccurrent flowing in the biasing transistor 402 is Ib′ when the biasingtransistor 402 is operating in the linear region, then Ib′<Ib.Consequently, the relationship between Vb and Vb′ becomes Vb′<Vb. Inother words, when Vin and Ib′ becomes small, then Vb′ also becomessmall. As a result, the input/output relationship (relationship betweenVin and Vout) becomes non-linear as shown in FIG. 7.

The following fact can be discerned from the above explanation.

First, to increase an amplitude value of the output electric potentialVout in the source follower circuit, it is appropriate to make the biaselectric potential Vb small. Since Vout=Vin−Vb, when Vb is small, theVout can be increased. However, it is necessary that the biasingtransistor 402 be in conductive. Therefore, the value of the biaselectric potential Vb must be made larger than that of a thresholdvoltage of the biasing transistor 402.

To the contrary, in the case the bias electric potential Vb is large,the biasing transistor 402 can readily operate in the linear region whenthe input electric potential Vin becomes small. As a result, theinput/output relationship of the source follower circuit is likely tobecome non-linear. It is appropriate, in this respect, to make the biaselectric potential Vb small.

The operation of the source follower circuit under a fixed normal statehas been explained so far. Next, the operation of the source followercircuit under a transient state will be explained. As a circuitstructure thereof, the circuit shown in FIG. 4 will be used with theaddition of a load. In other words, the circuit structure here is astructure in which a load capacitance 805 is connected between outputterminals, that is, a source terminal of an amplifying transistor 801and a load capacitance power source line 806 as shown in FIG. 8.Therefore, the electric potential of the load capacitance 805 is thesame as the output electric potential Vout of the source followercircuit.

First, a case where the output electric potential Vout is small in theinitial state, that is, when Vout<Vin−Vb. FIG. 8A is a diagram showing acircuit configuration, and FIG. 8B is a diagram showing a timing chart.In that case, a value of a voltage Vgs between a gate and a source of anamplifying transistor 801 is larger than a value of a voltage Vgsbetween a gate and a source of a biasing transistor 802. Therefore, alarge electric current flows in the amplifying transistor 801, and as aresult, a load capacitance 805 is rapidly charged and the outputelectric potential Vout becomes large, whereby the voltage Vgs betweenthe gate and the source of the amplifying transistor 801 becomessmaller. When the voltage Vgs between the gate and the source of theamplifying transistor 801 finally becomes equivalent to the biaselectric potential Vb, the transient state is turned into a fixed normalstate. The output electric potential Vout at that point isVout=Vin−Vgs=Vin−Vb. Thus, as in the case where Vout<Vin−Vb, initiallythe voltage Vgs between the gate and the source of the amplifyingtransistor 801 is large under the transient state. Therefore, a largeelectric current, passing through the amplifying transistor 801, flowsto the load capacitance 805. The writing-in time of a signal to the loadcapacitance 805 can thus be performed in a short time.

On the other hand, a case is discussed where the output electricpotential Vout is large in the initial state, that is, when Vout>Vin−Vb.FIG. 9A is a diagram showing a circuit configuration thereof, and FIG.9B is a diagram showing a timing chart thereof. In that case, because avalue of a voltage Vgs between a gate and a source of an amplifyingtransistor 901 is small, the amplifying transistor 901 is in anon-conductive state. Then, the electric charges that have accumulatedin a load capacitance 905 flow through a biasing transistor 902 tothereby be discharged. At that point, a voltage between a gate and asource of the biasing transistor 902 is the bias electric potential Vb,and therefore the electric current flowing in the biasing transistor 902becomes Ib. As the output electric potential Vout gradually becomessmaller, the voltage Vgs between the gate and the source of theamplifying transistor 901 becomes larger. When the voltage Vgs betweenthe gate and the source of the amplifying transistor 901 finally becomesequivalent to the bias electric potential Vb, the transient state isturned into the fixed normal state. Under the fixed normal state, thevalue of Vout is a fixed value, and hence an electric current will notflow in the load capacitance 905. The electric current Ib willcontinuously flow in the 2 transistors of the source follower circuit.

Thus, from the above explanation, it can be understood that whenVout>Vin−Vb, the electric discharging time of the load capacitance 905,that is, the signal writing-in time is determined by the electriccurrent Ib flowing through the biasing transistor 902. The amount of theelectric current Ib is determined by the size of the bias electricpotential Vb. Therefore, to increase the electric current in order toshorten the signal writing-in time to the load capacitance 905, it isnecessary to increase the bias electric potential Vb.

Next, a timing chart of a signal in a pixel 309 is shown in FIG. 10.First, the resetting transistor 307 is turned into a conductive state bycontrolling the reset signal line 305, whereby the electric potential ofthe N channel side terminal of the photo diode 304 is charged until theelectric potential Vd of the power source line 309. In other words, thepixel is reset. Subsequently, the resetting transistor 307 is turnedinto a non-conductive state by controlling the reset signal line 305.Thereafter, when light is irradiated to the photo diode 304, an electriccharge according to the light density is generated. Therefore, theelectric charge that is charged due to the resetting operation isgradually being discharged. In short, the electric potential of the Nchannel side terminal of the photo diode 304 decreases. In the case adark light is irradiated to the photo diode 304, the amount of electricdischarge is small, and therefore the electric potential of the Nchannel side terminal of the photo diode 304 does not decrease much.Then, at a certain point, the switching transistor 301 is turned into aconductive state to thereby read-out the electric potential of the Nchannel side terminal of the photo diode 304 as a signal. This signal isproportional to the density of light. Then, the resetting transistor 307is turned into the conductive state again to thereby reset the photodiode 304, and similar operations are repeated.

A transistor in the pixel 309 will be explained next. Regarding thepolarity of the transistor thereof, all are N channel types most of thetime. In rare cases, a P channel type may be used for the resettingtransistor (JIEC Seminar: Development Prospects of the CMOS Camera: Feb.20, 1998, refer to FIG. 11). Further, with regard to a method of liningup (arranging) the amplifying transistor and a selecting transistor, Nchannel types are used for both transistors and as shown in FIG. 3,often the structure is one in which the power source line 309 and theamplifying transistor 306 are connected, the amplifying transistor 306and the switching transistor 301 are connected, and the switchingtransistor 301 and the signal output line 303 are connected. In rarecases N channel types are used for both transistors and the structurethereof is one in which the power source line 309 and the switchingtransistor 301 are connected, the switching transistor 301 and theamplifying transistor 306 are connected, and the amplifying transistor306 and the signal output line 306 are connected (ISSCC97: p. 180, A ¼Inch 330K Square Pixel Progressive Scan CMOS Active Pixel Image Sensor).

Next, a sensor portion for performing photoelectric conversion or thelike will be explained. A PN type of photo diode is usually used toconvert light into electricity. However, there are other types includinga PIN type diode, an avalanche diode, an NPN incorporated diode, aSchottky diode, etc. There are also others such as a photo diode forX-rays and a sensor for infrared rays. These are described in “TheBasics of Solid Imaging Elements: DENSHINO MENO SHIKUMI” written byTakao Ando and Hirohito Kobuchi: Nippon Riko Shuppan Kai.

Products suitable as sensors will be explained next. Other than thedigital still camera and scanner, a sensor may also be used in an X-raycamera. In that case, there is a case where the photo diode for directlyconverting an X-ray into an electric signal is used or a case where anX-ray is converted into light by using a fluorescent material or ascintillator and then the light is read. The case of converting an X-rayinto light by using a scintillator and thereafter reading the light isdescribed in “Euro Display 99: p. 203: X-ray Detectors base on AmorphousSilicon Active Matrix”. In the “IEDM 98: p. 21: Amorphous Silicon TFTX-ray Image Sensors”, a case of reading light by using an amorphoussilicon is reported, and a case of reading light by using a photoconductor is reported in the “AM-LCD99: p. 45: Real-time Imaging FlatPanel X-ray Detector”.

First, consideration is made on the item required in a source followercircuit 405. The most necessary item is to obtain a value as large aspossible as an amplitude of the output electric potential Vout, that is,a value that is roughly equivalent to an amplitude of the input electricpotential Vin. If the amplitude of the output electric potential Vout islarge, signals having a large number of gradations can be obtained. As aresult, the quality of the image read from an image sensor is enhanced.In addition, it is necessary that the input/output relationship islinear. In other words, it is crucial that the relationship of the inputelectric potential Vin and the output electric potential Vout in thesource follower circuit operate linearly in a wide range. That is, therelationship of Vout=Vin−Vb is maintained even if the input electricpotential Vin is small. In short, it is important that the biasingtransistor 402 operate in the saturated region. Other items that arenecessary include a short signal writing-in time of the output electricpotential Vout to the load capacitance. If the signal writing-in time islong, the operation thereof will become slow.

Then, consideration is now made regarding a method to satisfy theabove-mentioned items required in the source follower circuit.

First, because Vout=Vin−Vb, it is appropriate to make the bias electricpotential Vb small in order to increase the amplitude of the outputelectric potential Vout. Similarly, the bias electric potential Vb maybe made small in order to widen the operating region of a linearinput/output relationship. The reason for this resides in that when thebias electric potential Vb is small, the biasing transistor 402 caneasily operate in the saturated region even if the output electricpotential has become small. However, when the bias electric potential Vbis small, the writing-in time of the output signal becomes long.

In other words, the amplitude of the output electric potential and thesignal writing-in time have a trade-off relationship. It is impossibleto shorten the writing-in time of the output electric potential whileincreasing the amplitude value of the output electric potential. Inaddition, it is also impossible to widen the operating region in whichthe input/output relationship is linear while increasing the amplitudevalue of the output electric potential.

SUMMARY OF THE INVENTION

The present invention has been made in view of the above problems, andtherefore has an object to solve the above problems of the prior art.

According to the present invention, in a source follower circuit thatemploys an N channel transistor, prior to outputting a signal therefrom,an output electric potential (electric potential of a load capacitance)is lowered once (in the case of a source follower circuit employing a Pchannel transistor, the output electric potential is raised).Hereinafter, the process of lowering the output electric potential(electric potential of the load capacitance) of the source followercircuit (in the case where a P channel is employed, increasing theelectric potential thereof) is referred to as “pre-discharge”, and aperiod during which the pre-discharge is performed is referred to as“pre-discharge period”. In the present invention, an actual signal isoutput after a pre-discharge.

Conventionally, in a source follower circuit employing an N channeltransistor, an electric charge of the load capacitance was dischargedthrough a biasing transistor when Vout>Vin−Vb in the initial state.However, in the present invention, the electric potential of the loadcapacitance is lowered once to thereby make the source follower circuitin a state where Vout<Vin−Vb. This operation is the pre-discharge.Thereafter, the actual signal is output. Since the follower circuit isalready in the state where Vout<Vin−Vb at the time of outputting theactual signal, the signal is output to the load capacitance through anamplifying transistor. Therefore, the signal writing-in time does notbecome long.

An electric potential that is slightly higher than a threshold voltageof the biasing transistor, that is, an electric potential value as lowas possible, is applied to a gate electric potential of the biasingtransistor when outputting the actual signal, in other words, the biaselectric potential Vb. The reasons for this resides in that consideringthe input/output relationship Vout=Vin−Vb of the source followercircuit, it is preferable to lower the bias electric potential Vb asmuch as possible in order to increase the output electric potentialVout. However, it is necessary that the biasing transistor be inconductive state. In short, it is necessary that the biasing transistoroperate in the saturated region. Accordingly, the gate electricpotential of the biasing transistor when outputting the actual signal,that is, the bias electric potential Vb is made slightly higher than thethreshold voltage of the biasing transistor. In practice, the electricpotential is made slightly higher than the highest threshold voltage inall the biasing transistors in a circuit.

Even if, the bias electric potential Vb is made small, and therefore theamount of electric current of the biasing transistor becomes small, theelectric charge of the load capacitance is not discharged through thebiasing transistor. Hence, the signal writing-in time does not becomelong. In addition, because the bias electric potential is small, theoperating region in which the input/output relationship is linear iswide. Therefore, it is possible to prevent the signal writing-in timefrom becoming long, and enlarging the amplitude of the output electricpotential and widening the operating region in which the input/outputrelationship is linear at the same time. The structure of the presentinvention will be described below.

According to the present invention, there is provided a semiconductordevice having an amplifying transistor, a biasing transistor, anamplifying side power source line, a biasing side power source line, abias signal line, an electric discharging transistor, and an electricdischarging power source line, characterized in that:

a drain terminal of the amplifying transistor is connected to theamplifying side power source line, a source terminal of the biasingtransistor is connected to the biasing side power source line, a sourceterminal of the amplifying transistor is connected to a drain terminalof the biasing transistor, a gate terminal of the biasing transistor isconnected to the bias signal line, a gate terminal of the amplifyingtransistor serves as an input terminal, and a source terminal of theamplifying transistor serves as an output terminal, and

one of the output terminal and the electric discharging power sourceline is connected to a source terminal of the electric dischargingtransistor while the other thereof is connected to a drain terminal ofthe electric discharging transistor.

According to the present invention, there is provided a semiconductordevice having an amplifying transistor, a biasing transistor, anamplifying side power source line, a biasing side power source line, anda bias signal line, characterized in that:

a drain terminal of the amplifying transistor is connected to theamplifying side power source line, a source terminal of the biasingtransistor is connected to the biasing side power source line, a sourceterminal of the amplifying transistor is connected to a drain terminalof the biasing transistor, a gate terminal of the biasing transistor isconnected to the bias signal line, a gate terminal of the amplifyingtransistor serves as an input terminal, and a source terminal of theamplifying transistor serves as an output terminal, and

a signal generating device is connected to the bias signal line forperforming the operation of making the electric potential of the biasingside power source line close to the electric potential of the amplifyingside power source line.

According to the present invention, there is provided a semiconductordevice, characterized in that one terminal of a load capacitance isconnected to the output terminal, and the other terminal of the loadcapacitance is connected to a load capacitance power source line.

According to the present invention, there is provided a semiconductordevice, characterized in that the electric discharging power source lineis connected to the biasing side power source line.

According to the present invention, there is provided a semiconductordevice, characterized in that at least 2 lines from among the electricdischarging power source line, the load capacitance power source line,and the biasing side power source line are connected together.

According to the present invention, there is provided a semiconductordevice, characterized in that the load capacitance power source line isconnected to the amplifying side power source line.

According to the present invention, there is provided a semiconductordevice, characterized in that the semiconductor device has at least oneselecting switch for controlling an electric current flowing to the loadcapacitance or the output terminal from the amplifying side power sourceline or from the biasing side power source line.

According to the present invention, there is provided a semiconductordevice, characterized in that the semiconductor device has at least oneselecting switch for controlling an electric current flowing to theoutput terminal from the amplifying side power source line or from thebiasing side power source line.

According to the present invention, there is provided a semiconductordevice, characterized in that the selecting switch has at least one ofan N channel transistor or a P channel transistor.

According to the present invention, there is provided a semiconductordevice, characterized in that an absolute value of a voltage between agate and a source of the biasing transistor is equivalent to a minimumvalue of an absolute value of a voltage between a gate and a source thatis necessary for making the biasing transistor into a conductive state.

According to the present invention, there is provided a semiconductordevice, characterized in that a photoelectric conversion element isconnected to the input terminal.

According to the present invention, there is provided a semiconductordevice, characterized in that a signal generated by a photoelectricconversion element is fed to the input terminal.

According to the present invention, there is provided a semiconductordevice, characterized in that the photoelectric conversion element iseither an X-ray sensor or an infrared sensor.

According to the present invention, there is provided a semiconductordevice, characterized in that the photoelectric conversion element isany one of a photo diode, a Schottky diode, an avalanche diode, or aphoto conductor.

According to the present invention, there is provided a semiconductordevice, characterized in that the photo diode is one of a typeincorporating a PN type, a PIN type, or an NPN embedded type.

According to the present invention, there is provided a semiconductordevice, characterized in that the semiconductor device has a resettingtransistor, and a source terminal or a drain terminal of the resettingtransistor is connected to the photoelectric conversion element.

According to the present invention, there is provided a semiconductordevice, characterized in that when the semiconductor device has aplurality of biasing transistors, an absolute value of a voltage betweena gate and a source of the plurality of biasing transistors isequivalent to a minimum value of an absolute value of a voltage betweena gate and a source that is necessary for making the entire plurality ofbiasing transistors into a conductive state.

According to the present invention, there is provided a semiconductordevice, characterized in that the amplifying transistor, the biasingtransistor, and the electric discharging transistor are transistorshaving the same polarity.

According to the present invention, there is provided a driving methodof a semiconductor device having an amplifying transistor, a biasingtransistor, an amplifying side power source line, a biasing side powersource line, and a bias signal line, characterized in that:

a drain terminal of the amplifying transistor is connected to theamplifying side power source line, a source terminal of the biasingtransistor is connected to the biasing side power source line, a sourceterminal of the amplifying transistor is connected to a drain terminalof the biasing transistor,

a gate terminal of the biasing transistor is connected to the biassignal line, a gate terminal of the amplifying transistor serves as aninput terminal, and a source terminal of the amplifying transistorserves as an output terminal, and characterized in that

the driving method outputs a signal after performing a pre-discharge.

According to the present invention, there is provided a driving methodof a semiconductor device having an amplifying transistor, a biasingtransistor, an amplifying side power source line, a biasing side powersource line, and a bias signal line, characterized in that:

a drain terminal of the amplifying transistor is connected to theamplifying side power source line, a source terminal of the biasingtransistor is connected to the biasing side power source line, a sourceterminal of the amplifying transistor is connected to a drain terminalof the biasing transistor, a gate terminal of the biasing transistor isconnected to the bias signal line, a gate terminal of the amplifyingtransistor serves as an input terminal, and a source terminal of theamplifying transistor serves as an output terminal, and characterized inthat

the driving method outputs a signal after performing a pre-discharge bymaking an electric potential of the biasing side power source line closeto an electric potential of the amplifying side power source line.

According to the present invention, there is provided a driving methodof a semiconductor device having an amplifying transistor, a biasingtransistor, an amplifying side power source line, a biasing side powersource line, and a bias signal line, an electric discharging transistor,and an electric discharging power source line characterized in that:

a drain terminal of the amplifying transistor is connected to theamplifying side power source line, a source terminal of the biasingtransistor is connected to the biasing side power source line, a sourceterminal of the amplifying transistor is connected to a drain terminalof the biasing transistor, a gate terminal of the biasing transistor isconnected to the bias signal line, a gate terminal of the amplifyingtransistor serves as an input terminal, a source terminal of theamplifying transistor serves as an output terminal, one of the outputterminal and the electric discharging power source line is connected toa source terminal of the electric discharging transistor while the otherthereof is connected to a drain terminal of the electric dischargingtransistor, and characterized in that the driving method outputs asignal after performing a pre-discharge by making the electricdischarging transistor into a conductive state.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that a value of an electricpotential of the electric discharging power source line takes a valuethat is between an electric potential of the bias signal line and anelectric potential of the biasing side power source line.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that one terminal of a loadcapacitance is connected to the output terminal, and the other terminalof the load capacitance is connected to a load capacitance power sourceline.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the electricdischarging power source line and the biasing side power source line areto be connected together.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that at least 2 lines fromamong the electric discharging power source line, the load capacitancepower source line, and the biasing side power source line are to beconnected together.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the load capacitancepower source line is connected to the amplifying side power source line.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the driving method of asemiconductor device has at least one selecting switch for controllingan electric current flowing to the load capacitance or the outputterminal from the amplifying side power source line or from the biasingside power source line.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the driving method of asemiconductor device has at least one selecting switch for controllingan electric current flowing to the output terminal from the amplifyingside power source line or from the biasing side power source line.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the selecting switchhas at least one of an N channel transistor or a P channel transistor.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that an absolute value of avoltage between a gate and a source of the biasing transistor isequivalent to a minimum value of an absolute value of a voltage betweena gate and a source that is necessary for making the biasing transistorinto a conductive state.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that a photoelectricconversion element is connected to the input terminal.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that a signal generated by aphotoelectric conversion element is fed to the input terminal.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the photoelectricconversion element is either an X-ray sensor or an infrared sensor.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the photoelectricconversion element is any one of a photo diode, a Schottky diode, anavalanche diode, or a photo conductor.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the photo diode is anyone of a type incorporating a PN type, a PIN type, or an NPN embeddedtype.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the driving method of asemiconductor device has a resetting transistor, and the resettingtransistor resets the photoelectric conversion element.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that when the driving methodof a semiconductor device has a plurality of biasing transistors, anabsolute value of a voltage between a gate and a source of the pluralityof biasing transistor is equivalent to a minimum value of an absoluteValue of a voltage between a gate and a source that is necessary formaking the entire plurality of biasing transistors into a conductivestate.

According to the present invention, there is provided a driving methodof a semiconductor device, characterized in that the amplifyingtransistor, the biasing transistor, and the electric dischargingtransistor are transistors having the same polarity.

BRIEF DESCRIPTION OF THE DRAWINGS

The above and other objects and features of the present invention willbe more apparent from the following description taken in conjunctionwith the accompanying drawings:

FIGS. 1A and 1B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIG. 2 is a diagram showing a circuit configuration of a pixel of aconventional passive sensor;

FIG. 3 is a diagram showing a circuit configuration of a pixel of aconventional active sensor;

FIG. 4 is a diagram showing a circuit configuration of a conventionalsource follower circuit;

FIG. 5 is a diagram showing an electric current characteristic of asource follower circuit;

FIG. 6 is a diagram showing an electric current characteristic of asource follower circuit;

FIG. 7 is a diagram showing an input/output characteristic of a sourcefollower circuit;

FIGS. 8A and 8B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit;

FIGS. 9A and 9B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit;

FIG. 10 is a diagram showing a timing chart of an active sensor;

FIGS. 11A and 11B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIGS. 12A and 12B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIGS. 13A and 13B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIGS. 14A and 14B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIGS. 15A and 15B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIGS. 16A and 16B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIGS. 17A and 17B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIGS. 18A and 18B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIGS. 19A and 19B are diagrams showing a circuit configuration and atiming chart, respectively, of a source follower circuit of the presentinvention;

FIG. 20 is a block diagram of an area sensor of the present invention;

FIG. 21 is a diagram showing a circuit configuration of a pixel of anactive sensor of the present invention;

FIG. 22 is a diagram showing a circuit configuration of a pixel of anactive sensor of the present invention;

FIG. 23 is a diagram showing a circuit configuration of a signalprocessing circuit of the present invention;

FIG. 24 is a diagram showing a circuit configuration of a final outputamplifying circuit signal of the present invention;

FIG. 25 is a diagram showing a circuit configuration of a final outputamplifying circuit signal of the present invention;

FIG. 26 is a diagram showing a timing chart of an area sensor of thepresent invention;

FIG. 27 is a diagram showing a timing chart of an area sensor of thepresent invention;

FIG. 28 is a diagram showing a timing chart of an area sensor of thepresent invention;

FIG. 29 is a diagram showing a circuit configuration of a signalprocessing circuit of the present invention;

FIGS. 30A to 30D are diagrams showing manufacturing processes of animage sensor of the present invention;

FIGS. 31A to 31D are diagrams showing manufacturing processes of animage sensor of the present invention;

FIGS. 32A to 32C are diagrams showing manufacturing processes of animage sensor of the present invention;

FIGS. 33A and 33B are diagrams showing manufacturing processes of animage sensor of the present invention;

FIGS. 34A and 34B are diagrams showing electronic equipments using theimage sensor of the present invention;

FIG. 35 is a diagram showing an electronic equipment using the imagesensor of the present invention;

FIG. 36 is a diagram showing an electronic equipment using the imagesensor of the present invention; and

FIG. 37 is a diagram showing an electronic equipment using the imagesensor of the present invention;

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS Embodiment Mode 1

A typical embodiment mode of the present invention is shown in thefollowing.

Shown in FIGS. 11A and 11B is an example of a pre-dischargeimplementation method. FIG. 11A is a diagram showing a circuitconfiguration of the pre-discharge implementation method, and FIG. 11Bis a diagram showing a signal timing chart thereof. In FIGS. 11A and11B, pre-discharge is performed by arranging an exclusive electricdischarging transistor 1108. FIGS. 11A and 11B are diagrams illustratingan example of a case in which an N channel transistor is used toconstruct the source follower circuit.

An electric potential of a gate terminal of an amplifying transistor1101 (input terminal 1105) becomes an input electric potential Vin. Thisinput electric potential Vin corresponds to an electric potential of anN channel side terminal of a photo diode. A drain terminal of theamplifying transistor 1101 is connected to an amplifying side powersource line 1103, and a source terminal thereof is connected to a drainterminal of a biasing transistor 1102. The source terminal of theamplifying transistor 1101 serves as an output terminal 1107 and anelectric potential thereof becomes an output electric potential Vout. Abias electric potential Vb is applied to a gate terminal of the biasingtransistor 1102. A source terminal of the biasing transistor 1102 isconnected to a biasing side power source line 1104. A source terminaland a drain terminal of the electric discharging transistor 1108 areconnected to the output terminal 1107 of the source follower circuit(source terminal of the amplifying transistor 1101) and an electricdischarging power source line 1109.

As shown in FIG. 11B, when the electric discharging transistor 1108 isin conductive, the electric potential of the output terminal 1107becomes the electric potential of the electric discharging power sourceline 1109 to thereby carry out pre-discharge. During a pre-dischargeperiod, a large electric current can be caused to flow to the electricdischarging transistor 1108 because the gate electric potential of theelectric discharging transistor 1108 is large. As a result, the outputelectric potential Vout can be rapidly lowered, whereby thepre-discharge period is shortened. In this method, the bias electricpotential Vb may be equivalent to that of the prior art, or may belarge.

An actual signal is output after the pre-discharge. In that case, sincethe source follower circuit is in the Vout<Vin−Vb state, a largeelectric current flows to the amplifying transistor 1101 as the voltagebetween the gate and the source thereof is large. Consequently, a signalwriting-in can be done in a short time.

Taking the input/output relationship of Vout=Vin−Vb into consideration,it is appropriate to make the bias electric potential Vb as low aspossible when outputting the output electric potential Vout in order toincrease the output electric potential Vout. However, the biasingtransistor 1102 must be in conductive. In other words, the biasingtransistor 1102 must be operable in the saturated region and a value inwhich a fixed electric current can flow therein. Therefore, other thanduring the pre-discharge period, an optimum value of an absolute valueof a bias signal electric potential (voltage between the gate and thesource of the biasing transistor) is an electric potential that isslightly higher than an absolute value of a threshold voltage of thebiasing transistor 1102.

Further, when the bias electric potential Vb is low, the operatingregion in which the input/output relationship is linear can be widenedbecause the biasing transistor 1102 can readily operate in the saturatedregion.

Thus, from the above consequences, it is possible to prevent the signalwriting-in time from becoming long, and enlarging the amplitude of theoutput electric potential and widening the operating region in which theinput/output relationship is linear can be realized at the same time.

With regard to the polarity of the electric discharging transistor 1108,the polarity thereof may be similar to those of the amplifyingtransistor 1101 and the biasing transistor 1102, that is, in FIGS. 11Aand 11B, an N channel type. The reason for this resides in that whenmaking the electric discharging transistor 1108 into a conductive, if anN channel type is used to form the electric discharging transistor 1108,then the voltage between the gate and the source thereof can largebecause the electric potential of the electric discharging power sourceline 1109 is low. If the polarity of the electric discharging transistor1108 is different from that of the amplifying transistor 1101 and thatof the biasing transistor 1102, that is, in FIGS. 11A and 11B, if a Pchannel type is used to form the electric discharging transistor 1108,it is necessary to apply an extremely low electric potential to the gateterminal of the electric discharging transistor 1108. In other words, itis necessary to apply an electric potential that is lower than theelectric potential of the biasing side power source line 1104.Therefore, from the above explanation, it is desirable to make thepolarity of the electric discharging transistor 1108 similar to that ofthe amplifying transistor 1101 and that of the biasing transistor 1102.

Note that in FIGS. 11A and 11B, a plurality of electric dischargingtransistors 1108N may be used, in which case transistors of bothpolarities may be used.

Next, the electric potential of the electric discharging power sourceline 1109 will be explained. To perform pre-discharge is to set thestate of the circuit to Vout<Vin−Vb. Therefore, the electric potentialof the electric discharging power source line 1109 has to be set to alow electric potential. The electric potential thereof may be lower thanthe electric potential of the biasing side power source line 1104.However, since the electric potential operation range of the outputterminal 1107 is between the electric potential of the amplifying sidepower source line 1103 and the electric potential of the biasing sidepower source line 1104. Even if the electric potential of the electricdischarging power source line 1109 is made lower than the electricpotential of the biasing side power source line 1104, no improvement isobtained. In the case where the electric potential of the electricdischarging power source line 1109 is higher than the electric potentialof the biasing side power source line 1104, the state of Vout<Vin−Vb maynot be attained if the electric potential of the electric dischargingpower source line 1109 is made higher than the electric potential of thebias signal line 1106. Thus, from the above explanation, it is necessarythat the electric potential of the electric discharging power sourceline 1109 be set higher than the electric potential of the biasing sidepower source line 1104 but lower than the electric potential of the biassignal line 1106. Normally, the electric potential of the electricdischarging power source line 1109 may be set equivalent to that of thebiasing side power source line 1104. Therefore, the electric dischargingpower source line 1109 and the biasing side power source line 1104 maybe connected.

When employing the circuit of FIGS. 11A and 11B in practice, the loadcapacitance is often connected to the output terminal 1107 to therebyaccumulate the signals therein. The diagram of a circuit configurationof a case in which the load capacitance is connected to the circuitillustrated in FIGS. 11A and 11B is shown in FIGS. 1A and 1B. Oneterminal of a load capacitance 110 is connected to an output terminal107 whereas the other terminal thereof is connected to a loadcapacitance power source line 111. The electric potential value of theload capacitance power source line 111 may be an arbitrary value.Normally the electric potential value thereof is often set equivalent tothe electric potential of a biasing side power source line 104.Therefore, the load capacitance power source line 111 and the biasingside power source line 104 may be connected. The load capacitance powersource line 111 may also be connected with an amplifying side powersource line 103. Thus, from the above explanation, 2 lines or more fromamong the load capacitance power source line 111, the biasing side powersource line 104, and the electric discharging power source line 109 maybe connected to each other. A circuit configuration and a timing chartof a situation where 3 lines are connected to each other is shown inFIGS. 12A and 12B.

Explanation has been given so far for the case of using an N channeltransistor to construct the source follower circuit. However, it is alsopossible to use a P channel transistor to construct the source followercircuit. Thus, a drawing of circuit configuration using the P channeltransistor to construct the source follower circuit will be shown next.The case of using the P channel transistor in the circuit of FIGS. 11Aand 11B will be shown in FIGS. 13A and 13B, and a case of using the Pchannel transistor in the circuit of FIGS. 1A and 1B will be shown inFIGS. 14A and 14B. Shown in FIGS. 15A and 15B is a case of using the Pchannel transistor in the circuit of FIGS. 12A and 12B. When the Nchannel transistor is used to construct the source follower circuit, theelectric potential of the amplifying side power source line 1103 ishigher than the biasing side power source line 1103. However, when the Pchannel transistor is used to construct the source follower circuit, theelectric potential of an amplifying side power source line 1303 is lowerthan the electric potential of a biasing side power source line 1304.

In some cases, a plurality of source follower circuits may be arrangedand output terminals may be connected to each other and arrangedtherein. At that point, there is a necessity to output a signal onlyfrom one source follower circuit. Therefore, a switch may be provided tostop the flow of an electric current. The diagrams of a circuitconfiguration and a timing chart of a case where a transferringtransistor 1612 is provided between an output terminal 1607 and a loadcapacitance 1610 in the circuit of FIGS. 1A and 1B is illustrated inFIGS. 16A and 16B. In the circuit of FIGS. 16A and 16B, a switchingtransistor 1713 is provided between an output terminal 1707 and anamplifying transistor 1701, and the circuit configuration and timingchart of this case is illustrated in FIGS. 17A and 17B. In FIGS. 16A and16B or in FIGS. 17A and 17B, at least one element from the amplifyingtransistor, the biasing transistor, and the selecting switch may be usedto construct a unit pixel.

Note that the switch for stopping the flow of an electric current may beformed of either the N channel transistor or the P channel transistor.In addition, a plurality of switches may be provided and the connectingmethod thereof may be in series or in parallel.

Embodiment Mode 2

Next, an embodiment mode of a case in which a method of performing thepre-discharge is different from that of Embodiment Mode 1 is shown inFIGS. 18A and 18B. FIG. 18A is a diagram showing a circuitconfiguration, and FIG. 18B is a diagram showing a signal timing chart.In FIGS. 18A and 18B, pre-discharge is performed by making the biaselectric potential Vb large. Shown in FIGS. 18A and 18B is an example ofa case using an N channel transistor to construct the source followercircuit.

An electric potential of a gate terminal of an amplifying transistor1801 becomes the input electric potential Vin. This input electricpotential Vin corresponds to the electric potential of the N channelside terminal of the photo diode. A drain terminal of the amplifyingtransistor 1801 is connected to an amplifying side power source line1803, and a source terminal thereof is connected to a drain terminal ofa biasing transistor 1802. The source terminal of the amplifyingtransistor 1801 serves as an output terminal 1807 and an electricpotential thereof becomes the output electric potential Vout. The biaselectric potential Vb is applied to a gate terminal of the biasingtransistor 1802. A source terminal of the biasing transistor 1802 isconnected to a biasing side power source line 1804.

The bias electric potential Vb is increased during the pre-dischargeperiod. As a result, the electric potential of the output terminal 1807becomes the electric potential of a biasing side power source line 1804to thereby carry out pre-discharge. During the pre-discharge period, alarge electric current can be caused to flow to the biasing transistor1802 because the gate electric potential of the biasing transistor 1802,that is, the bias electric potential Vb is large. Consequently, theoutput electric potential Vout can be rapidly lowered, whereby thepre-discharge period is shortened.

An actual signal is output after the pre-discharge. In that case, sincethe source follower circuit is in the Vout<Vin−Vb state, a largeelectric current flows to the amplifying transistor 1801 because theelectric potential between the gate and the source thereof is large.Consequently, the signal writing-in can be done in a short time.

Taking the input/output relationship of Vout=Vin−Vb into consideration,it is appropriate to make the bias electric potential Vb as low aspossible when outputting the output electric potential Vout in order toincrease the output electric potential Vout. However, the biasingtransistor 1802 must be in conductive. In other words, the biasingtransistor 1802 must be operable in the saturated region and set at avalue in which a fixed electric current can flow therein. Therefore,other than during the pre-discharge period, an optimum value of anabsolute value of a bias signal electric potential (voltage between thegate and the source of the biasing transistor) is an electric potentialthat is slightly higher than an absolute value of a threshold voltage ofthe biasing transistor 1802.

Further, when the bias electric potential Vb is low, the operatingregion in which the input/output relationship is linear can be widenedbecause the biasing transistor 1802 can readily operate in the saturatedregion.

Thus, from the above consequences, it is possible to prevent the signalwriting-in time from becoming long, and enlarging the amplitude of theoutput electric potential while widening the operating region in whichthe input/output relationship is linear can be realized at the sametime.

Regarding the electric potential value of the bias electric potential Vbduring pre-discharge, it is preferable to make the electric potentialvalue thereof as high as possible in order to perform discharge.Therefore, increasing the bias electric potential Vb until it is as highas the highest electric potential in the circuit, for example, theamplifying side power source line 1803, is appropriate.

In the prior art, a fixed electric potential was applied to the biassignal line 1806. In Embodiment Mode 2, the bias electric potential Vbchanges during pre-discharge. Therefore, a signal generating device forchanging the bias electric potential Vb is connected to the bias signalline 1806.

The explanation so far has been about the case of using an N channeltransistor to construct the source follower circuit. However, it is alsopossible to use a P channel transistor to construct the source followercircuit. Thus, a drawing where the P channel transistor is used toconstruct the source follower circuit is shown in FIGS. 19A and 19B.Similar to Embodiment Mode 1, the relationship concerning the size ofthe electric potential of the amplifying side power source line and theelectric potential of the biasing side power source line is differentbetween the case of using the N channel transistor to construct thesource follower circuit and the case of using the P channel transistorto construct the source follower circuit.

Note that similar to Embodiment Mode 1, the provision of a loadcapacitance and a selecting switch is also possible in Embodiment Mode2.

Embodiment 1

An embodiment of a case in which pre-discharge is performed by employingan electric discharging transistor in an area sensor that has pixelsarranged two-dimensional therein and incorporated with driver circuitsin the periphery thereof will be explained next. The entire circuitconfiguration is illustrated in FIG. 20. First, there is provided apixel arrangement portion 2005 having pixels arranged two-dimensionaltherein. Driver circuits for driving a gate signal line and a resetsignal line of each of the pixels is provided on the left and rightsides of the pixel arrangement portion 2005. In FIG. 20, a gate signalline driver circuit 2006 is provided on the left side and a reset signalline driver circuit 2007 is provided on the right side. Driver circuitssuch as a signal processing circuit are arranged above the pixelarrangement portion 2005. A biasing circuit 2003 is arranged above thepixel arrangement portion 2005 in FIG. 20. The biasing circuit 2003 andthe amplifying transistors of the respective pixels form the sourcefollower circuit. A sample hold and signal processing circuit 2002 arearranged above the biasing circuit 2003. Circuits for maintainingsignals for a time, for performing analog/digital conversion, or forreducing noise are arranged here. A signal output line driver circuit2001 is arranged above the sample hold and signal processing circuit2002. The signal output line driver circuit 2001 outputs signals foroutputting, in sequence, the signals that have been temporarilypreserved. Then, before the signals are output to the outside, a finaloutput amplifying circuit 2004 is arranged thereto. Before the signals,which are sequentially output hereto by the sample hold and the signalprocessing circuit 2002 and the signal output line driver circuit 2001,are output to the outside, the signals are amplified by the final outputamplifying circuit 2004. Therefore, although unnecessary when thesignals are not amplified, in practice it is often provided.

Next, the circuit configuration of the respective portions isillustrated. First, taking an ith line jth row pixel portion circuit2008 as an example from the interior of the pixel arrangement portion2005 having pixels arranged in two-dimensional, the circuitconfiguration thereof is shown in FIG. 21. In FIG. 21, the ith line jthrow pixel portion circuit 2008 is composed of a P channel resettingtransistor 2107, a P channel switching transistor. 0.2101, an N channelamplifying transistor 2106, and a photoelectric conversion element(here, it is the most typical photo diode 2104). A P channel sideterminal of the photo diode 2104 is connected to a power source standardline 2112, and an N channel side terminal thereof is connected to a gateterminal of the amplifying transistor 2106. An ith line resetting signalline 2105 is connected to a gate terminal of the resetting transistor2107. A source terminal and a drain terminal of the resetting transistor2107 are connected to a jth row power source line 2109 and to the gateterminal of the amplifying transistor 2106. A gate terminal of theswitching transistor 2101 is connected to an ith line gate signal line2102, and a source terminal and a drain terminal thereof are connectedto the jth row power source line 2109 and to the gate terminal of theamplifying transistor 2106. A source terminal and a drain terminal ofthe amplifying transistor 2106 are connected to a jth row signal outputline 2103 and to the switching transistor 2101. As in the prior art, theith line gate signal line 2102 and the ith line resetting signal line2105 have their wirings extended in the horizontal direction.

If the wirings of this circuit configuration is made corresponding tothe wirings of the source follower circuit, the jth row power sourceline 2109 corresponds to the amplifying side power source line 1103, thepower source standard line 2112 corresponds to the biasing side powersource line 1104, and the output terminal 1107 corresponds to the jthrow signal output line 2103.

In FIG. 21, the resetting transistor 2107 is formed of the P channeltype. However, the resetting transistor 2107 may be formed of the Nchannel type. Note that, the voltage between the gate and the source ofthe resetting transistor 2107 cannot be large during the resettingoperation in the case the N channel type is used to form the resettingtransistor 2107. Accordingly, the resetting transistor will operate inthe saturated region, whereby the photo diode 2104 cannot be chargedsufficiently. As a result, though the resetting transistor 2107 willoperate even if it is formed of the N channel type, it is desirable touse a P channel type.

As for the switching transistor 2101, it is arranged between the ithline power source line 2109 and the amplifying transistor 2106, and isdesirably formed of the P channel type as well. However, similar to theprior art, since the switching transistor can operate even if it isformed of N channel type, the N channel type may be used. The switchingtransistor 2101 may also be provided between the jth row signal outputline 2103 and the amplifying transistor 2106. However, because there isdifficulty in outputting a signal correctly, the switching transistor2101 is arranged between the ith line power source line 2109 and theamplifying transistor 2106, and is desirably formed of the P channeltype.

As for the amplifying transistor 2106 in FIG. 21, the N channel type isused. Nonetheless, the P channel type may be used. However, in the caseof using the P channel type, it is necessary to change the connectionmethod of the circuit in order to combine the amplifying transistor withthe biasing transistor to thereby operate as the source followercircuit. That is, in the circuit configuration of FIG. 21, theamplifying transistor 2106 will not operate by simply changing thepolarity thereof.

Then, an example of a circuit configuration when a P channel type ofamplifying transistor is used is shown in FIG. 22. The differencesbetween this circuit configuration and that of FIG. 21 is that thepolarity of an amplifying transistor 2206 is the P channel type, thedirection in which the photo diode faces is inverted, and the powersource line and the power source standard line are changed. In the caseof using the P channel type in the amplifying transistor, it isnecessary to use the P channel type in the biasing transistor also. Thereason for this resides in that there is a necessity to operate thebiasing transistor as a fixed electric current source. Therefore, adescription of a biasing transistor 2211 is also made in FIG. 22 forreference. The ith line jth row pixel portion circuit 2008 illustratedin FIG. 22 is composed of an N channel type resetting transistor 2207,an N channel type switching transistor 2201, a P channel type amplifyingtransistor 2206, and a photoelectric conversion element (here, it is themost typical photo diode 2204). An N channel side terminal of the photodiode 2204 is connected to a power source line 2209, and a P channelside terminal thereof is connected to agate terminal of an amplifyingtransistor 2206. An ith line resetting signal line 2205 is connected toa gate terminal of the resetting transistor 2207. A source terminal anda drain terminal of the resetting transistor 2207 are connected to a jthrow power source standard line 2212 and to the gate terminal of theamplifying transistor 2206. A gate terminal of the switching transistor2201 is connected to an ith line gate signal line 2202, and a sourceterminal and a drain terminal thereof are connected to the jth row powersource standard line 2212 and the amplifying transistor 2206. A sourceterminal and a drain terminal of the amplifying transistor 2206 areconnected to a jth row signal output line 2203 and to the switchingtransistor 2201. A biasing signal line 2210 is connected to a gateterminal of the biasing transistor 2211, and a source terminal and agate terminal thereof are connected to the jth row signal output line2203 and to the power source line 2209.

When the wirings of this circuit configuration is made corresponding tothe wirings of the source follower circuit, then the jth row powersource standard line 2212 corresponds to the amplifying side powersource line 1803, the power source line 2109 corresponds to the biasingside power source line 1804, and the output terminal 1807 corresponds tothe jth row signal output line 2203.

In FIG. 22, the N channel type is used for the resetting transistor2207. However, the resetting transistor 2207 may also be formed of the Pchannel type. However, the voltage between the gate and the source ofthe resetting transistor 2207 cannot be large during the resettingoperation in the case where the P channel type is used to form theresetting transistor 2207. Accordingly, the resetting transistor willoperate in the saturated region, whereby the photo diode 2204 cannot becharged sufficiently. As a result, though the resetting transistor 2207will operate even if the P channel type is used, it is desirable to usethe N channel type.

As for the switching transistor 2201 in FIG. 22, it is arranged betweenthe jth row power source standard line 2212 and the amplifyingtransistor 2206, and desirably is formed of N channel type as well.However, since the switching transistor can operate even if it is formedof the P channel type, the P channel type may also be used. Theswitching transistor 2201 may also be provided between the jth rowsignal output line 2203 and the amplifying transistor 2206. However,because there is difficulty in outputting a signal correctly, theswitching transistor 2201 is arranged between the jth row power sourcestandard line 2212 and the amplifying transistor 2206, and is desirablyformed by using the N channel type.

Thus, as is apparent from the comparison between the circuitconfigurations of FIGS. 21 and 22, when the polarity of the amplifyingtransistors is different, the optimal transistor structure also differs.

Next, the circuit configuration of a jth row peripheral portion circuit2009 taken as an exemplary row of circuits from inside the biasingcircuit 2003 and the sample hold and signal processing circuit 2002 isshown in FIG. 23. A biasing transistor 2311 is arranged in the biasingcircuit 2003. The polarity thereof is the same as the polarity of theamplifying transistor of the respective pixels. Therefore, if theamplifying transistor of the pixel is the N channel type, the biasingtransistor is also the N channel type. In FIG. 23, the biasingtransistor 2311 is the N channel type. A gate terminal of the biasingtransistor 2311 is connected to a biasing signal line 2310, and a sourceterminal and a drain terminal thereof are connected to a jth row signaloutput line 2303 and a power source standard line 2312 (when the biasingtransistor is the P channel type, the power source line is used in placeof the power source standard line). The biasing transistor 2311 and theamplifying transistors of the respective pixels, operates as the sourcefollower circuit. A gate terminal of a transferring transistor 2313 isconnected to a transfer signal line 2314, and a source terminal and adrain terminal thereof are connected to a jth row signal output line2303 and a load capacitance 2315. The transferring transistor isoperated when transferring the electric potential of the signal outputline 2303 to the load capacitance 2315. Therefore, a P channel typetransferring transistor may be added and connected in a row to an Nchannel type transferring transistor 2314. The load capacitance 2315 isconnected to the transferring transistor 2313 and the power sourcestandard line 2312. The role of the load capacitance 2315 is totemporarily accumulate therein the signals output from the signal outputline 2303. A gate terminal of an electric discharging transistor 2316 isconnected to a pre-discharge signal line 2317, and a source terminal anda drain terminal thereof are connected to the load capacitance 2315 andthe power source standard line 2312. Prior to inputting the electricpotential of the signal output line 2303 to the load capacitance 2315,the electric discharging transistor 2316 operates to discharge theelectric charges that have temporarily accumulated in the loadcapacitance 2315.

Note that the analog/digital signal conversion circuit, the noisereduction circuit, etc. may also be arranged therein.

A final selecting transistor 2319 is connected between the loadcapacitance 2315 and a final output line 2320. A source terminal and adrain terminal of the final selecting transistor 2319 are connected tothe load capacitance 2315 and the final output line 2320, and a gateterminal thereof is connected to a jth row final selecting line 2318.The final selecting line will be scanned from the first row in sequence.Then the jth row final selecting line 2318 is selected, and when thefinal selecting transistor 2319 is turned into conductive, the electricpotential of the load capacitance 2315 and that of the final output line2320 become equivalent. As a result, the signals that have accumulatedin the load capacitance 2315 can be output to the final output line2320. However, if electric charges are accumulated in the final outputline 2320 before outputting the signals to the final output line 2320,the electric potential when outputting the signals to the final outputline 2320 will be adversely influenced by those electric charges.Therefore, the electric potential of the final output line 2320 must beinitialized to a certain electric potential value before the signals areoutput to the final output line 2320. In FIG. 23, a final resettingtransistor 2322 is arranged between the final output line 2320 and thepower source standard line 2312. A gate terminal of the final resettingtransistor 2322 is connected to a jth row final resetting line 2321.Prior to selecting the jth row final selecting line 2318, the jth rowfinal resetting line 2321 is selected to thereby initialize the electricpotential of the final output line 2320 and that of the power sourcestandard line 2312. Thereafter, the jth row final selecting line 2318 isselected, whereby the signals that have accumulated in the loadcapacitance 2315 are output to the final output line 2320.

The signals that will be output to the final output line 2320 may bewithdrawn to the outside. However, because the signals are faint, thesignals are frequently amplified before being withdrawn to the outside.As a circuit for carrying out the amplification of the signals, thecircuit configuration of the final portion circuit 2010 is shown in FIG.24. There are various kinds of circuits for amplifying the signals, suchas an arithmetic amplifier. Any kind of circuit that can amplify thesignals may be used. As the most simple circuit configuration, thesource follower circuit is shown here. In FIG. 24, the N channel type isillustrated. Signals that are input to the final output amplifyingcircuit 2004 will be input to a final output line 2402. Signals areoutput from the first row in sequence from the final output line 2402.The signals are amplified by the final output amplifying circuit 2004and then output to the outside. The final output line 2402 is connectedto a gate terminal of a final output amplifier-amplifying transistor2404. A drain terminal of the final output amplifier-amplifyingtransistor 2404 is connected a power source line 2404, and a sourceterminal thereof serves as an output terminal. A gate terminal of afinal output amplifier-biasing transistor 2403 is connected to a finaloutput amplifying bias signal line 2405, and a source terminal and adrain terminal thereof are connected to a power source standard line2407 and a source terminal of the final output amplifier-amplifyingtransistor 2404.

Shown in FIG. 25 is a circuit configuration of the source followercircuit when the P channel type is used. The difference from the circuitconfiguration of FIG. 24 is that the power source line and the powersource standard line are reversed. A final output line 2502 is connectedto a gate terminal of a final output amplifier-amplifying transistor2504. A drain terminal of the final output amplifier-amplifyingtransistor 2504 is connected to a power source standard line 2507, and asource terminal thereof serves as an output terminal. A gate terminal ofa final output amplifier-biasing transistor 2503 is connected to a finaloutput amplifying bias signal line 2505. A source terminal and a drainterminal of the final output amplifier-biasing transistor 2503 areconnected to a power source line 2506 and a source terminal of the finaloutput amplifier-amplifying transistor 2504. A value of the electricpotential of the final output amplifying bias signal line 2505 isdifferent from that of the final output amplifying bias signal line 2405in the case where the N channel type is used.

In FIGS. 24 and 25, the source follower circuit is constructed of onlyone level. However, it may also be constructed of plural levels. Forexample, in the case of constructing the source follower circuit in 2levels, the output terminal of the first level may be connected to theinput terminal of the second level. In addition, in each of the levels,either the N channel type or the P channel type may be used.

The gate signal line and reset signal line driver circuit 2006, thepower source line driver circuit 2207, and a signal output line drivercircuit AZ01 are circuits which simply output pulse signals. Therefore,implementation thereof can be made by employing a known technique.

A timing chart of a signal will be explained next. The timing chart ofthe circuit shown in FIG. 20 is illustrated in FIG. 26. The reset signalline is scanned sequentially from the first line. For example, first an(i−1)th line is selected, followed by an ith line, and then an (i+1)thline is selected. A period until the same line is selected againcorresponds to a frame period. Similarly, the gate signal line issequentially scanned from the first line. However, the timing to startscanning the gate signal line is later than the timing to start scanningthe reset signal line. For instance, directing the attention to a pixelof the ith line, the ith line reset signal line is selected, andthereafter the ith line gate signal line is selected. When the ith linegate signal line is selected, a signal is output from the pixel of theith line. A period from the time the pixel is reset until the signal isoutput becomes an accumulation time. During the accumulation time,electric charges generated by light are being accumulated in the photodiode. The timing to reset and the timing to output a signal aredifferent in each line. Therefore, although the accumulation time of thepixels in all the lines are equivalent, the time that signals areaccumulated therein is different.

Next, the timing chart of a signal of FIG. 23 is shown in FIG. 27.Because the operation is repetitious, the time that the ith line gatesignal line is selected will be taken as an example and observed. First,after the ith line gate signal line 2102 is selected, the pre-dischargesignal line 2317 is selected to thereby make the electric dischargingtransistor 2316 in conductive. Subsequently, the transfer signal line2314 is selected, whereby the signal of each of the rows from the ithline pixel is output to the load capacitance 2315 of every row.

After accumulating the signals of all the pixels of the ith line in theload capacitance 2315 of every row, the signals of every row aresequentially output to the final output line 2320. During the periodfrom the time the transfer signal line 2314 has become non-selective tothe time the gate signal line is selected, all the rows are scanned bythe signal output line driver circuit 2001. First, the final reset lineof the first row is selected to thereby make the final resettingtransistor 2322 into conductive, whereby the electric potential of thefinal output line 2320 is initialized to that of the power sourcestandard line 2312. Thereafter, the final selecting line 2318 of thefirst row is selected and the final selecting transistor 2319 is turnedinto conductive to thereby output the signal in the load capacitance2315 of the first row to the final output line 2320. Next, the finalreset line of the second row is selected to thereby make the finalresetting transistor 2322 into conductive, whereby the electricpotential of the final output line 2320 is initialized to that of thepower source standard line 2312. Thereafter, the final selecting line2318 of the second row is selected and the final selecting transistor2319 is turned into conductive to thereby output the signal in the loadcapacitance 2315 of the second row to the final output line 2320. Theoperation is repeated thereafter. Similarly, in the case of the jthline, the final reset line of the jth row is selected to thereby makethe final resetting transistor 2322 into conductive, whereby theelectric potential of the final output line 2320 is initialized to thatof the power source standard line 2312. Thereafter, the final selectingline 2318 of the jth row is selected and the final selecting transistor2319 is turned into conductive to thereby output the signal in the loadcapacitance 2315 of the jth row to the final output line 2320. Next, thefinal reset line of the (j+1)th row is selected and the final resettingtransistor 2322 is turned into conductive, whereby the electricpotential of the final output line 2320 is initialized to that of thepower source standard line 2312. Thereafter, the final selecting line2318 of the (j+1)th row is selected and the final selecting transistor2319 is turned into conductive to thereby output the signal in the loadcapacitance 2315 of the (j+1)th row to the final output line 2320. Thesame operation is repeated thereafter to sequentially output all thesignals to the final output line. During this operation, the bias signalline 2310 is fixed. The signals output to the final output line 2320 areamplified by the final output amplifying circuit 2004 and then output tothe outside.

Next, the (i+1)th line gate signal line is selected. The same operationas performed when the ith line gate signal line was selected will beperformed. Then, the gate signal line of the next line will be selectedfurther and the same operation will be repeated.

The electric potential of the bias signal line 2310 will be explainedhere. In FIG. 23, a plural number of the biasing transistor 2311 isprovided. Therefore, even if there is a fluctuation in the thresholdvoltages of the plural number of the biasing transistor 2311, all thebiasing transistors 2311 must be in conductive. As a result, it isnecessary to make the absolute value of the voltage between the gate andthe source of the biasing transistor equivalent to the minimum value ofthe absolute value of the voltage between the gate and the sourcethereof in order to turn all the biasing transistors into conductive.

Note that as for the sensor portion in which photoelectric conversion isperformed, other than the usual PN type of photo diode, a PIN typediode, an avalanche diode, an NPN incorporated diode, a Schottky diode,an X-ray photo conductor, and a sensor for infrared rays or the like maybe used. In addition, X-rays may be converted into light by using afluorescent material or a scintillator and thereafter read the lightthat has been converted.

As explained so far, the photoelectric conversion element is oftenconnected to the input terminal of the source follower circuit. However,a switch may be sandwiched therebetween like a photo gate type, or thesignal, after it has been processed so that it is a logarithmic value oflight density, maybe input to the input terminal, like a logarithmconversion type.

Although the area sensor having pixels arranged in two-dimensionaltherein was explained in Embodiment 1, a line sensor having pixelsarrange in one-dimensional can also be realized.

Embodiment 2

In Embodiment 2, a case in which pre-discharge is performed bycontrolling a bias signal line in an area sensor that has pixelsarranged in two-dimensional therein and incorporated with drivercircuits in the periphery thereof will be explained next. The Embodiment2 is different from Embodiment 1 only with respect to a portion of thecircuit configuration (FIG. 23) and a portion of the signal timing chart(FIG. 27). Therefore, a circuit configuration thereof corresponding tothat of FIG. 23 is shown in FIG. 29, and a timing chart of a signalthereof corresponding to that of FIG. 27 is shown in FIG. 28.

The circuit configuration of FIG. 29 is one in which the electricdischarging transistor 2316 and the pre-discharge signal line 2317 areremoved from the circuit configuration of FIG. 23.

Next, the timing chart of a signal in FIG. 29 is shown in FIG. 28.Because the operation is repetitious, the case in which the ith linegate signal line is selected will be taken as an example and observed.First, after the ith line gate signal line 2102 is selected, theelectric potential of a bias signal line 2910 and that of a transferringtransistor 2913 are raised to thereby perform pre-discharge. Then theelectric potential of the bias signal line 2910 is returned to itsoriginal value, whereby the signal of each of the rows from the ith linepixels is output to a load capacitance 2915 of every row. The signal ofeach of the rows is sequentially output to a final output line 2920after the signals of all the ith line pixels have accumulated in theload capacitance 2915 of every row.

Note that in Embodiment 2, the bias electric potential Vb changes duringpre-discharge. Therefore, a signal generating device for changing thebias electric potential Vb may be connected to the bias signal line2910.

Embodiment 3

A method of manufacturing a sensor portion using TFT on the glass ofthis invention is explained using FIGS. 30 to 33.

First, as shown in FIG. 30A, a base film 201 is formed to a thickness of300 nm on a glass substrate 200. A silicon oxinitride film is laminatedas the base film 201 in Embodiment 3. At this point, it is appropriateto set the nitrogen concentration to between 10 and 25 wt % in the filmcontacting the glass substrate 200. In addition, it is effective thatthe base film 201 has a thermal radiation effect, and a DLC(diamond-like carbon) film may also be provided.

Next, an amorphous silicon film (not shown in the figure) is formed witha thickness of 50 nm on the base film 201 by a known deposition method.Note that it is not necessary to limit to the amorphous silicon film,and a semiconductor film containing an amorphous structure (including amicrocrystalline semiconductor film) may be used. In addition, acompound semiconductor film containing an amorphous structure, such asan amorphous silicon germanium film, may also be used. Further, the filmthickness may be made from 20 to 100 nm.

The amorphous silicon film is then crystallized by a known technique,forming a crystalline silicon film (also referred to as apolycrystalline silicon film or a polysilicon film) 202. There arethermal crystallization using an electric furnace, laser annealingcrystallization using a laser light, and lamp annealing crystallizationusing an infrared light as known crystallization methods.Crystallization is performed in Embodiment 3 using an excimer laserlight, which uses XeCl gas.

Note that pulse emission excimer laser light formed into a linear shapeis used in Embodiment 3, but a rectangular shape may also be used.Continuous emission type argon laser light and continuous emission typeexcimer laser light can also be used.

In this embodiment, although the crystalline silicon film is used as theactive layer of the TFT, it is also possible to use an amorphous siliconfilm as the active layer.

Note that it is effective to form the active layer of the transistor forreset, in which there is a necessity to reduce the off current, by theamorphous silicon film, and to form the active layer of the transistorfor amplification by the crystalline silicon film. Electric currentflows with difficulty in the amorphous silicon film because the carriermobility is low, and the off current does not easily flow. In otherwords, the most can be made of the advantages of both the amorphoussilicon film, through which current does not flow easily, and thecrystalline silicon film, through which current easily flows.

Next, as shown in FIG. 30B, a protective film 203 is formed on thecrystalline silicon film 202 with a silicon oxide film having athickness of 130 nm. This thickness may be chosen within the range of100 to 200 nm (preferably between 130 and 170 nm). Furthermore, anotherfilms such as insulating films containing silicon may also be used. Theprotective film 203 is formed so that the crystalline silicon film isnot directly exposed to plasma during addition of an impurity, and sothat it is possible to have delicate concentration control of theimpurity.

Resist masks 204 a, 204 b, and 204 c are then formed on the protectivefilm 203, and an impurity element, which imparts n-type conductivity(hereafter referred to as an n-type impurity element), is added throughthe protective film 203. Note that elements residing in periodic tablegroup 15 are generally used as the n-type impurity element, andtypically phosphorous or arsenic can be used. Note that a plasma dopingmethod is used, in which phosphine (PH₃) is plasma-excited withoutseparation of mass, and phosphorous is added at a concentration of1×10¹⁸ atoms/cm³ in Embodiment 3. An ion implantation method, in whichseparation of mass is performed, may also be used, of course.

The dose amount is regulated such that the n-type impurity element iscontained in n-type impurity regions (b) 205 a, 205 b thus formed bythis process, at a concentration of 2×10¹⁶ to 5×10¹⁹ atoms/cm³(typically between 5×10¹⁷ and 5×10¹⁸ atoms/cm³).

Next, as shown in FIG. 30C, the protective film 203 and the resist masks204 a, 204 b, and 204 c are removed, and an activation of the addedn-type impurity elements is performed. A known technique of activationmay be used as the means of activation, but activation is done inEmbodiment 3 by irradiation of excimer laser light (laser annealing). Ofcourse, a pulse emission excimer laser and a continuous emission excimerlaser may both, be used, and it is not necessary to place any limits onthe use of excimer laser light. The goal is the activation of the addedimpurity element, and it is preferable that irradiation is performed atan energy level at which the crystalline silicon film does not melt.Note that the laser irradiation may also be performed with theprotective film 203 in place.

The activation of impurity elements by heat treatment (furnaceannealing) may also be performed along with activation of the impurityelement by laser light. When activation is performed by heat treatment,considering the heat resistance of the substrate, it is good to performheat treatment at about 450 to 550° C.

A boundary portion (connecting portion) with end portions of the n-typeimpurity regions (b) 205 a, 205 b, namely regions, in which the n-typeimpurity element is not added, on the periphery of the n-type impurityregions (b) 205 a, 205 b, is delineated by this process. This meansthat, at the point when the TFTs are later completed, extremely goodconnecting portion can be formed between LDD regions and channel formingregions.

Unnecessary portions of the crystalline silicon film are removed next,as shown in FIG. 30D, and island-shape semiconductor films (hereinafterreferred to as active layers) 206 to 210 are formed.

Then, as shown in FIG. 31A, a gate insulating film 211 is formed,covering the active layers 206 to 210. An insulating film containingsilicon and with a thickness of 10 to 200 nm, preferably between 50 and150 nm, may be used as the gate insulating film 211. A single layerstructure or a lamination structure may be used. A 110 nm thick siliconoxinitride film is used in Embodiment 3.

Thereafter, a conductive film having a thickness of 200 to 400 nm isformed and patterned to form gate electrodes 212 to 216. In Embodiment3, the gate electrodes and wirings (hereinafter referred to as gatewirings) electrically connected to the gate electrodes for providingconductive paths are formed of the same materials. Of course, the gateelectrode and the gate wiring may be formed of different materials fromeach other. More specifically, the gate wirings are made of a materialhaving a lower resistivity than the gate electrodes. This is because amaterial enabling fine processing is used for the gate electrodes, whilethe gate wirings are formed of a material that can provide a smallerwiring resistance but is not suitable for fine processing. The wiringresistance of the gate wiring can be made extremely small by using thistype of structure, and therefore a sensor portion having a large surfacearea can be formed. Namely, the above described pixel structure isextremely effective when an area sensor with a sensor portion having ascreen size of a 10 inch diagonal or larger (in addition, a 30 inch orlarger diagonal) is realized.

Although the gate electrode can be made of a single-layered conductivefilm, it is preferable to form a lamination film with two layers orthree layers, if necessary. Any known conductive films can be used forthe gate electrodes 212 to 216.

Typically, it is possible to use a film made of an element selected fromthe group consisting of aluminum (Al), tantalum (Ta), titanium (Ti),molybdenum (Mo), tungsten (W), chromium (Cr), and silicon (Si), a filmof nitride of the above element (typically a tantalum nitride film,tungsten nitride film, or titanium nitride film), an alloy film ofcombination of the above elements (typically Mo—W alloy or Mo—Ta alloy),or a silicide film of the above element (typically a tungsten silicidefilm or titanium silicide film). Of course, the films may be used as asingle layer or a laminate layer.

In Embodiment 3, a laminate film of a tungsten nitride (WN) film havinga thickness of 30 nm and a tungsten (W) film having a thickness of 370nm is used. This may be formed by sputtering. When an inert gas such asXe or Ne is added as a sputtering gas, film peeling due to stress can beprevented.

The gate electrodes 213 and 216 are respectively formed at this time soas to overlap a portion of the n-type impurity regions (b) 205 a and 205b through the gate insulating film 211. This overlapping portion laterbecomes an LDD region overlapping the gate electrode.

Next, an n-type impurity element (phosphorous is used in Embodiment 3)is added in a self-aligning manner with the gate electrodes 212 to 216as masks, as shown in FIG. 31B. The addition is regulated such thatphosphorous is added to n-type impurity regions (c) 217 to 224 thusformed at a concentration of 1/10 to 1/2 that of the n-type impurityregions (b) 205 a and 205 b (typically between 1/4 and 1/3).Specifically, a concentration of 1×10¹⁶ to 5×10¹⁸ atoms/cm³ (typically3×10¹⁷ to 3×10¹⁸ atoms/cm³) is preferable.

Resist masks 225 a to 225 c are formed next, with a shape covering thegate electrodes 212, 214 and 215, as shown in FIG. 31C, and an n-typeimpurity element (phosphorous is used in Embodiment 3) is added, formingimpurity regions (a) 226 to 233 containing phosphorous at highconcentration. Ion doping using phosphine (PH₃) is also performed here,and the phosphorous concentration of these regions is regulated so as tobe set to from 1×10²⁰ to 1×10²¹ atoms/cm³ (typically between 2×10²⁰ and5×10²¹ atoms/cm³).

A source region or a drain region of the n-channel TFT is formed by thisprocess, and in the n-channel TFT, a portion of the n-type impurityregions (c) 217, 218, 222, and 223 formed by the process of FIG. 31B isremained. These remaining regions correspond to LDD regions.

Next, as shown in FIG. 31D, the resist masks 225 a to 225 c are removed,and new resist masks 234 a and 234 b are formed. A p-type impurityelement (boron is used in Embodiment 3) is then added, forming p-typeimpurity regions 235 and 236 containing boron at high concentration.Boron is added here at a concentration of 3×10²⁰ to 3×10²¹ atoms/cm³(typically between 5×10²⁰ and 1×10²¹ atoms/cm³) by ion doping usingdiborane (B₂H₆).

Note that phosphorous has already been added to the impurity regions 235and 236 at a concentration of 1×10²⁰ to 1×10²¹ atoms/cm³, but boron isadded here at a concentration of at least 3 times or more that of thephosphorous. Therefore, the n-type impurity regions already formedcompletely invert to p-type, and function as p-type impurity regions.

Next, after removing the resist masks 234 a and 234 b, the n-type orp-type impurity elements added to the active layer at respectiveconcentrations are activated. Furnace annealing, laser annealing or lampannealing can be used as a means of activation. In Embodiment 3, heattreatment is performed for 4 hours at 550° C. in a nitrogen atmospherein an electric furnace.

At this time, it is important to eliminate oxygen from the surroundingatmosphere as much as possible. This is because an exposed surface ofthe gate electrode is oxidized, which results in an increased resistanceif only a small amount of oxygen exists. Accordingly, the oxygenconcentration in the surrounding atmosphere for the activation processis set at 1 ppm or less, preferably at 0.1 ppm or less.

A first interlayer insulating film 237 is formed next, as shown in FIG.32A. A single layer insulating film containing silicon is used as thefirst interlayer insulating film 237, or a lamination film may be used.Further, a film thickness of between 400 nm and 1.5 μm may be used. Alamination structure of a silicon oxide film having a thickness of 800nm on a silicon oxinitride film having a thickness of 200 nm thick isused in Embodiment 3.

In addition, heat treatment is performed for 1 to 12 hours at 300 to450° C. in an atmosphere containing between 3 and 100% hydrogen,performing hydrogenation. This process is one of hydrogen termination ofdangling bonds in the semiconductor film by hydrogen, which is thermallyexcited. Plasma hydrogenation (using hydrogen excited by plasma) mayalso be performed as another means of hydrogenation.

Note that the hydrogenation processing may also be inserted during theformation of the first interlayer insulating film 237. Namely, hydrogenprocessing may be performed as above after forming the 200 nm thicksilicon oxinitride film, and then the remaining 800 nm thick siliconoxide film may be formed.

Next, a contact hole is formed in the gate insulating film 211 and thefirst interlayer insulating film 237, and source wirings 238 to 242 anddrain wirings 243 to 247 are formed. In this embodiment, this electrodeis made of a laminate film of three-layer structure in which a titaniumfilm having a thickness of 100 nm, an aluminum film containing titaniumand having a thickness of 300 nm, and a titanium film having a thicknessof 150 nm are continuously formed by sputtering. Of course, otherconductive films may be used.

A first passivation film 248 is formed next with a thickness of 50 to500 nm (typically between 200 and 300 nm). A 300 nm thick siliconoxinitride film is used as the first passivation film 248 in Embodiment3. This may also be substituted by a silicon nitride film. Note that itis effective to perform plasma processing using a gas containinghydrogen such as H₂ or NH₃ before the formation of the siliconoxinitride film. Hydrogen activated by this preprocess is supplied tothe first interlayer insulating film 237, and the film quality of thefirst passivation film 248 is improved by performing heat treatment. Atthe same time, the hydrogen added to the first interlayer insulatingfilm 237 diffuses to the lower side, and the active layers can behydrogenated effectively.

Next, a second interlayer insulating film 249 made of organic resin isformed as shown in FIG. 32B. As the organic resin, it is possible to usepolyimide, polyamide, acryl, BCB (benzocyclobutene) or the like.Especially, since the second interlayer insulating film 249 is primarilyused for leveling, acryl excellent in leveling properties is preferable.In this embodiment, an acrylic film is formed to a thickness sufficientto level a stepped portion formed by TFTs. It is appropriate that thethickness is made 1 to 5 μm (more preferably, 2 to 4 W.

Next, a contact hole is formed in the second interlayer insulating film249 and the first passivation film 248 so as to reach the drain wiring245, and a cathode electrode 250 of a photodiode is formed so as tocontact the drain wiring 245. In embodiment 3, an aluminum film formedby sputtering is used as the cathode electrode 250, but other metals,for example titanium, tantalum, tungsten, and copper can also be used.Further, a lamination film made from titanium, aluminum, and titaniummay also be used.

Patterning is next performed after depositing an amorphous silicon filmcontaining hydrogen over the entire surface of the substrate, and aphotoelectric conversion layer 251 is formed. Then, a transparentconductive film is formed on the entire surface of the substrate. A 200nm thick ITO film is deposited by sputtering as the transparentconductive film in Embodiment 3. The transparent conductive film ispatterned, forming an anode electrode 252. (FIG. 32C.)

A third interlayer insulating film 253 is then formed, as shown in FIG.33A. A level surface can be obtained by using a resin such as polyimide,polyamide, polyimide amide, or acrylic as the third interlayerinsulating film 253. A polyimide film having a thickness of 0.7 μm isformed over the entire surface of the substrate as the third interlayerinsulating film 253 in Embodiment 3.

A contact hole is next formed in the third interlayer insulating film253 so as to reach the anode electrode 252, and a sensor wiring 254 isformed. A 300 nm thick aluminum alloy film (an aluminum film comprisingtitanium of 1 wt %) is formed in Embodiment 3.

The sensor substrate is formed which has the structure as shown in FIG.33B.

Reference numeral 270 shows an amplifier TFT, 271 shows a switching TFT,272 shows reset TFT, 273 shows a bias TFT, and 274 shows discharge TFT.

In embodiment 3, the amplifier TFT 270 and the bias TFT 273 are ann-channel TFT, and both of source region side and drain region side haveLDD regions 281-282 and 284-285. Note that the LDD regions 281-282 and284-285 do not overlap with the gate electrodes 212 and 215 through thegate insulating film 211. The above constitution of the amplifier TFT270 and the bias TFT 273 can reduce the hot carrier injection as much aspossible.

Further in Embodiment 3, the switching TFT 271 and the discharge TFT 274is a n-channel TFT, each TFTs has LDD regions 283 and 286 on only thedrain region side. The LDD region 283 and 286 are overlapped to the gateelectrode 213 and 216 interposing the gate insulating film 211.

The formation of the LDD regions 283 and 286 on only the drain regionside is in consideration of reducing the hot carrier injection and notcausing the operating speed to drop. Further, it is not necessary to betoo concerned with the value of the off current for the switching TFT271 and the discharge TFT 274, and more importance may be placed on theoperating speed. It is therefore preferable for the LDD regions 283 and286 to completely overlap with the gate electrodes 213 and 216, and toreduce resistive components as much as possible. Namely, the so-calledoffset should be eliminated. In particular, when the source signal linedriver circuit or the gate signal line driving circuit is driven at 15Vto 20V, the above constitution of the discharge TFT 274 of Embodiment 3is effective to reduce the hot carrier injection and also not to dropthe operation speed.

Furthermore, in Embodiment 3, a reset TFT 272 is p-channel TFT and hasno LDD region. Degradation due to hot carrier injection is almost of noconcern for the p-channel TFTs, and therefore LDD regions do not have tobe formed in particular. It is also possible, of course, to form an LDDregion similar to that of an n-channel TFT to take action against hotcarriers. Further, the reset TFT 272 may be an n-channel type TFT.

The device is completed as a manufactured product by attaching aconnector (flexible printed circuit, FPC) for connecting terminalspulled around from the elements or circuits formed on the substrate withexternal signal terminals.

The sensor is formed by using a TFT on the glass or the photodiode inthis embodiment, the transistor on the single crystalline siliconsubstrate can also be used.

Embodiment 4

The sensor manufactured by implementing the present invention can beused for various kinds of electronic equipments. The following can begiven as such electronic equipment according to the present invention: ascanner; a digital still camera; an x-ray camera; a portable informationterminal (a mobile computer, a portable telephone, and a portable gamemachine); a notebook type personal computer; a game apparatus; a videotelephone, etc.

FIG. 34A is a scanner, and contains a reading region 3402, a sensorportion 3401, a reading operation start switch 3404 and the like. Thepresent invention can be used as the sensor portion 3401.

FIG. 34B is a digital still camera, and contains a finder 3405, a sensorportion 3404, a shutter button 3406 and the like. The present inventioncan be used as the sensor portion 3404.

FIG. 35 is an x-ray camera, and contains an x-ray generator 3501, asensor portion 3503, a computer 3054 for signal processing and the like.An object 3502 to be examined stands between the x-ray generator 3501and the sensor portion 3503, and the x-ray photograph is taken. Thepresent invention can be used as the sensor portion 3503.

FIG. 36 is a personal computer, and contains a main body 3601, a casing3602, a display 3603, a keyboard 3604, a sensor portion 3605 and thelike. The present invention can be used as the display 3603 and thesensor portion 3605.

Here, FIG. 37 shows a portable telephone, and contains a main body 3701,a sound output portion 3702, a sound input portion 3703, a display 3704,operation switches 3705, an antenna 3706 and a sensor portion 3707. Thepresent invention can be used as the sensor portion 3707.

The present invention enables enlarging of the amplitude of the outputwhile preventing the writing-in time of the output electric potential ofthe source follower circuit from becoming long. Further, at the sametime, the present invention can widen the operating region in which theinput/output relationship of the source follower circuit is linear.Consequently, an area sensor having a high image quality is realized.

What is claimed is:
 1. (canceled)
 2. An X-ray system comprising: anX-ray generator configured to irradiate an object with an X-ray; asensor portion configured to sense light; and a computer configured toprocess a signal which is generated in response to the light sensed bythe sensor portion, wherein the sensor portion comprises a circuitincluding a transistor, a photoelectric conversion element over thetransistor, a resin film over the photoelectric conversion element,wherein a channel forming region of the transistor is overlapped by thephotoelectric conversion element.
 3. The X-ray system according to claim2, wherein the transistor is a p-channel transistor.
 4. The X-ray systemaccording to claim 2, wherein the transistor has no LDD region.
 5. TheX-ray system according to claim 2, wherein the photoelectric conversionelement comprises a cathode electrode, a photoelectric conversion layerover the cathode electrode, and an anode electrode over thephotoelectric conversion layer.
 6. The X-ray system according to claim2, wherein the light is the X-ray through the object.
 7. The X-raysystem according to claim 2, wherein the X-ray through the object isconverted into the light by using a fluorescent material or ascintillator.
 8. The X-ray system according to claim 2, wherein theresin film comprises polyimide, polyamide, polyimide amide, or acrylic.9. An X-ray system comprising: an X-ray generator configured toirradiate an object with an X-ray; a sensor portion configured to senselight; and a computer configured to process a signal which is generatedin response to the light sensed by the sensor portion, wherein thesensor portion comprises a circuit including a transistor, an organicresin film over the transistor, a photoelectric conversion element overthe organic resin film, a resin film over the photoelectric conversionelement, wherein a channel forming region of the transistor isoverlapped by the photoelectric conversion element.
 10. The X-ray systemaccording to claim 9, wherein the transistor is a p-channel transistor.11. The X-ray system according to claim 9, wherein the transistor has noLDD region.
 12. The X-ray system according to claim 9, wherein thephotoelectric conversion element comprises a cathode electrode, aphotoelectric conversion layer over the cathode electrode, and an anodeelectrode over the photoelectric conversion layer.
 13. The X-ray systemaccording to claim 9, wherein the light is the X-ray through the object.14. The X-ray system according to claim 9, wherein the X-ray through theobject is converted into the light by using a fluorescent material or ascintillator.
 15. The X-ray system according to claim 9, wherein theresin film comprises polyimide, polyamide, polyimide amide, or acrylic.16. The X-ray system according to claim 9, wherein the organic resinfilm comprises polyimide, polyamide, acryl, benzocyclobutene.
 17. TheX-ray system according to claim 9, wherein the thickness of the organicresin film is 1 to 5 mm.
 18. An X-ray system comprising: an X-raygenerator configured to irradiate an object with an X-ray; a sensorportion configured to sense light; and a computer configured to processa signal which is generated in response to the light sensed by thesensor portion, wherein the sensor portion comprises a circuit includinga transistor, a photoelectric conversion element over the transistor, apolyimide film over the photoelectric conversion element, wherein achannel forming region of the transistor is overlapped by thephotoelectric conversion element.
 19. The X-ray system according toclaim 18, wherein the transistor is a p-channel transistor.
 20. TheX-ray system according to claim 18, wherein the transistor has no LDDregion.
 21. The X-ray system according to claim 18, wherein thephotoelectric conversion element comprises a cathode electrode, aphotoelectric conversion layer over the cathode electrode, and an anodeelectrode over the photoelectric conversion layer.
 22. The X-ray systemaccording to claim 18, wherein the light is the X-ray through theobject.
 23. The X-ray system according to claim 18, wherein the X-raythrough the object is converted into the light by using a fluorescentmaterial or a scintillator.